A dc-dc power converter with improved output current resolution

ABSTRACT

The present invention relates to a DC-DC power converter which comprises a switched converter core operated in accordance with a primary control signal to supply a primary DC output current (Io) of the converter; said primary control signal exhibiting a minimum resolution, e.g. a minimum time step, leading to a corresponding minimum current step of the primary DC output current. The DC-DC power converter additionally comprises a controllable resistive path, or a controllable current source, connected between a pair of terminals selected from a group of: (the positive output terminal, the negative output terminal, the positive input terminal, the negative input terminal) and configured to add or subtract a secondary DC output current (Icon) to the primary DC output current (Io) in accordance with a secondary control signal to adjust the load current.

The present invention relates to a DC-DC power converter which comprisesa switched converter core operated in accordance with a primary controlsignal to supply a primary DC output current (Io) of the converter; saidprimary control signal exhibiting a minimum resolution, e.g. a minimumtime step, leading to a corresponding minimum current step of theprimary DC output current. The DC-DC power converter additionallycomprises a controllable resistive path, or a controllable currentsource, connected between a pair of terminals selected from a group of:(the positive output terminal, the negative output terminal, thepositive input terminal, the negative input terminal) and configured toadd or subtract a secondary DC output current (Icon) to the primary DCoutput current (Io) in accordance with a secondary control signal toadjust the load current.

BACKGROUND OF THE INVENTION

Power density and conversion efficiency are typically key performancemetrics of a power converter such as AC-DC, DC-AC and DC-DC powerconverter assemblies where it is desirable to achieve small physicalsize and high efficiency for a given output power specification.Resonant power converters are well-known types of DC-DC switched modepower supplies or converters (SMPS). Resonant power converters areparticularly useful for high switching frequencies such as above 1 MHzwhere switching losses of standard SMPS topologies (Buck, Boost etc.)tend to be unacceptable for conversion efficiency reasons. Resonantpower converters include a semiconductor switch arrangement, oftenincluding one or several MOSFET(s), GaN(s), SiCor or IGBT switches,relying on the resonances of circuit capacitances and inductances toshape the waveform of either the current or the voltage across theswitching element(s) such that, when switching takes place, there is nocurrent through and/or voltage across the switching element(s). Henceswitching loss is largely eliminated in at least some of the intrinsiccapacitances of the input switching element such that a dramaticincrease of the switching frequency becomes feasible for example tovalues at and above 3 MHz, 5 MHz or 10 MHz. This feature is known in theart under designations like zero voltage and/or current switching (ZVSand/or ZCS) operation. Commonly used switched mode power convertersoperating under ZVS and/or ZCS are often designated class E, class F orclass DE inverters or power converters.

Existing DC-DC power converters are often unable to supply asufficiently accurate current to a load at small output current levelsdue to a lack of adequate resolution of the output current of theconverter. Output current resolution limits are often imposed by aminimum time resolution of control pulses of a modulated switch controlsignal operating a switched converter core. The modulated switch controlsignal may comprise duty-cycle or ON-OFF modulation or PWM (pulse widthmodulation) that are commonly applied for DC output voltage control orDC output current control in DC-DC power converter designs. Even thoughimproved time resolution of the control pulses, and hence better DCoutput current resolution, may be achieved by using high-end controlcircuits, such as a microprocessor, FPGA, this will add undesirablecomplexity and costs to the DC-DC power converter.

The present invention addresses and solves inter alia problemsassociated with the inadequate output current resolution of existingDC-DC power converters.

SUMMARY OF THE INVENTION

A first aspect of the invention relates to a DC-DC power convertercomprising:

a primary side circuit comprising a positive input terminal and anegative input terminal for receipt of a DC input voltage,

a secondary side circuit comprising a positive output terminal and anegative output terminal for supply of a load current to a load. TheDC-DC power converter further comprising:

a switched converter core operated in accordance with a primary controlsignal to supply a primary DC output current (Io) of the converter; saidprimary control signal exhibiting a minimum resolution, e.g. a minimumtime step, leading to a corresponding minimum current step of theprimary DC output current,

a controllable resistive path, or a controllable current source,connected between a pair of terminals selected from a group of: (thepositive output terminal, the negative output terminal, the positiveinput terminal, the negative input terminal) and configured to add, i.e.source, or subtract, i.e. sink a secondary DC output current (Icon) tothe primary DC output current (Io) in accordance with a secondarycontrol signal to adjust the load current (Iload).

The switched converter core may comprise controllable switch arrangementwhich may comprise one, two or even more interconnected semiconductorswitches controlled by the primary control signal. The primary controlsignal may comprise a modulated switch control signal such as a PWMmodulated switch control signal or voltage, a PDM modulated switchcontrol voltage, a PAM modulated switch control voltage, aduty-cycle/burst-mode modulated switch control voltage. Each of thesemiconductor switches of the controllable switch arrangement maycomprise a transistor such as a bipolar junction transistor or a MOSFET.The MOSFET may comprise a NMOS transistor, or a Gallium Nitride (GaN)MOSFET or Silicon Carbide (SiC) MOSFET or IGBT. The control terminal,e.g. a gate or base, of each of the one, two or more semiconductorswitches may be coupled to, and driven by, the primary control signal orcontrol signal derived therefrom to alternatingly force thesemiconductor switch in question between on-states and off-states. Anoutput of the controllable switch arrangement may be connected to aresonant network and excite the resonant network at, or around, afundamental resonance frequency of the network. The skilled person willunderstand that the secondary side circuit may comprise a rectificationcircuit which is configured to convert an AC output voltage or currentof the controllable switch arrangement, or of the resonant network, intoa corresponding DC output voltage or current.

In one embodiment the controllable resistive path, or the controllablecurrent source, is connected between the positive output terminal andnegative output terminal. In another embodiment, the controllableresistive path, or the controllable current source, is connected betweenthe positive output terminal and positive input terminal. According toyet another embodiment, the controllable resistive path, or thecontrollable current source, is connected between the negative outputterminal and negative input terminal. Alternatively, the controllableresistive path, or the controllable current source, may be connectedbetween the positive input terminal and negative input terminal. Thesecondary control signal may be configured to adjust a resistance of thecontrollable resistive path to control the secondary DC output current.The secondary control signal may alternatively be configured adjust acurrent level or magnitude of the controllable current source andthereby directly adjust the secondary DC output current. Thecontrollable current source may comprise a multibit current DAC. Thelevel or magnitude of the secondary DC output current supplied by thecontrollable current source is substantially independent of the voltageacross the current source in contrast to the controllable resistive pathin which the respective voltages at the input and output terminals inquestion determine the magnitude of the secondary DC output current.

The resistance of the controllable resistive path may comprise atransistor, e.g. MOSFET operating in its linear region or operating intriode-mode such that the drain-source region provides an adjustableresistance. A control terminal of the transistor, e.g. gate or base, ispreferably connected to the secondary control signal. The secondary DCoutput current may be adjustable between a minimum current and a maximumcurrent by adjusting the resistance of the controllable resistive path.The secondary control signal may comprise a DC voltage or a modulatedcontrol voltage such as a PWM modulated voltage, a PDM modulatedvoltage, duty-cycle/burst-mode modulated voltage, i.e. on/off controlledcontrol voltage, etc.

The modulated control voltage is preferably derived from a multibitcontrol value or signal for controlling a modulation of the PWMmodulated voltage or a modulation of the PDM modulated voltage or amodulation of the burst-mode modulated voltage. The multibit controlsignal may comprise a predetermined number of steps. The step size mayset a minimum time resolution of the modulated control voltage and incertain embodiments also fixate a resolution of the resistance of thecontrollable resistive path. The resolution of the resistance of thecontrollable resistive path may set the minimum value of the secondaryDC output current and the maximum value of the secondary DC outputcurrent.

If the controllable current source comprises the multibit current DAC,the secondary control signal may be a digital signal or digital valuesetting or defining the current level or magnitude sourced by themultibit current DAC or sunk by the multibit current DAC.

According to one embodiment the minimum step of the primary DC outputcurrent is substantially equal to the maximum value of the secondary DCoutput current. This may be achieved by appropriate design of theadjustable resistance and the secondary control signal.

If the secondary DC output current is supplied by thepreviously-mentioned controllable current source, the latter may beconnected between the pair of terminals selected from the group of: (thepositive output terminal, the negative output terminal, the positiveinput terminal, the negative input terminal).

The skilled person will understand that certain a converter topologyselected from a group of {class E, class F, class DE, class EF, LLC,LCC, SEPIC}. The resonant power converter may comprise a galvanicisolation barrier to provide electrical insulation between primary sidecircuitry and secondary side circuitry of the power converter assembly.A galvanically isolated resonant power converter may comprise differenttypes of galvanic isolation barriers for example a pair of magneticallycoupled inductors that may be arranged as a transformer. The resonantpower converter may comprise a so-called self-oscillating topology wherea feedback loop is extending from the output of the controllable switcharrangement to a control terminal of at least one of the one or moresemiconductor switches of the controllable switch arrangement. Thefeedback loop is configured to induce self-oscillation in the resonantDC-DC power converter for example by designing the feedback loop withappropriate loop gain and loop phase characteristics.

Additional embodiments of the invention are recited by the furtherdependent claims appended below.

BRIEF DESCRIPTION OF THE DRAWINGS

A preferred embodiment of the invention will be described in more detailin connection with the appended drawings, in which:

FIG. 1 is a block diagram illustrating various exemplary embodiments ofthe present DC-DC power converter,

FIG. 2 is a block diagram of a DC-DC power converter in accordance witha first embodiment of the invention,

FIG. 3 is a block diagram of a DC-DC power converter in accordance witha second embodiment of the invention,

FIG. 4 shows a block diagram of a DC-DC power converter in accordancewith a third embodiment of the invention,

FIG. 4A is a block diagram of a DC-DC power converter in accordance witha fourth embodiment of the invention,

FIG. 5 illustrates the improved resolution of the load current providedby a controllable resistive path of the DC-DC power converter; and

FIG. 6 shows a transistor level diagram of an exemplary switchedconverter core based on a class E converter.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS

In the following, various exemplary embodiments of the present DC-DCpower converter assembly are described with reference to the appendeddrawings. The skilled person will understand that the accompanyingdrawings are schematic and simplified for clarity and therefore merelyshow details which are essential to the understanding of the invention,while other details have been left out. Like reference numerals refer tolike elements or components throughout. Like elements or components willtherefore not necessarily be described in detail with respect to eachfigure. It will further be appreciated that certain actions and/or stepsmay be described or depicted in a particular order of occurrence whilethose skilled in the art will understand that such specificity withrespect to sequence is not actually required.

FIG. 1 is a schematic diagram illustrating various exemplary embodimentsof the present DC-DC power converter 100 in a single drawing. The DC-DCpower converter 100 comprises a primary side circuit which comprises apositive input terminal 102 and a negative input terminal 104 forreceipt of a DC input voltage Vin. A secondary side circuit comprises apositive output terminal 112 and a negative output terminal 114 forsupply of a DC voltage and a load current to a load, LOAD, of the powerconverter. The load may generally exhibit inductive, capacitive orresistive impedance and may include a LED diode assembly as discussedbelow.

A switched converter core 105 is operated in accordance with a primarycontrol signal (not shown) to supply a primary DC output current (Io) ofthe switched converter core 105. The level of the primary DC outputcurrent (Io) may be set or controlled by a current regulation loop (notshown) which generates the primary control signal. The switchedconverter core 105 of the DC-DC power converter 100 may comprise anon-resonant or a resonant converter. The resonant converter maycomprise a converter topology selected from the group {class E, class F,class DE, class EF, LLC, LCC, SEPIC}. Certain embodiments of theswitched converter core 105 may comprise a galvanic isolation barriercoupling the primary side circuit to the secondary side circuit e.g. asdiscussed below in additional detail. The primary control signal maycomprise a modulated switch control signal such as a PWM modulatedswitch control signal or voltage, a PDM modulated switch control signal,a PAM modulated switch control signal or a duty-cycle/burst-modemodulated switch control signal. If the DC-DC power converter 100comprises a resonant converter, the switched converter core 105 may beconfigured with a switching frequency above 1 MHz, or above 5 MHz, orabove 10 MHz, or even at or above 20 MHz—for example in the VHF range.The switched converter core may comprise a self-oscillating class Econverter or a self-oscillating class F converter, or a self-oscillatingclass DE converter.

The modulated switch control signal often exhibits a minimum time step(1 LSB) leading to a corresponding minimum step of the primary DC outputcurrent (Io). This minimum time step or time resolution may for examplecorrespond to a minimum width of pulse of a PWM modulated switch controlsignal. For example, a common 8-bit PWM modulated control signal foroperating the switched converter core may have 256 pulse width steps ofresolution corresponding to 0.39% of a maximum width of the controlpulse. Hence, if the desired or target maximum output current of theswitched converter core is 1 A, then the minimum step or resolution ofthe output current (Io) is 3.9 mA. The consequence of this minimum stepor resolution of the output current is graphically illustrated by graph500 of FIG. 5 showing the smallest and next-smallest steps of the DCoutput current corresponding to digital values 0×01 and 0×02 of the PWMmodulated control signal. Hence, in the above case, the minimum step orresolution of the DC output current of the switched converter core is3.9 mA. The smallest increment of the output current from this minimumvalue of 3.9 mA is 7.8 mA—under the assumption that only the PWMmodulated control signal is available to adjust the DC output current ofthe power converter and hence also the load current (Iload). For allpractical switch-mode DC-DC converter designs there will be a limit tothe minimum PWM ON time, even with high-resolution PWM ICs, resulting ina finite or minimum resolution of the DC output current and thereforealso a minimum DC output current and a minimum current step. At lowerlevels of the DC output current the DC-DC power converter is switchedcompletely off. This is, however, a disadvantage if the DC-DC powerconverter is utilized to supply drive current to a LED based load. Inthe latter type of lightning applications low-level output currentperformance is important due to the high sensitivity of the human eye atlow light levels. Smaller steps of the DC output current (i.e. higherresolution) leads to an improvement of the perceptual quality of theLED/lamp. Therefore, it is desirable to extend the control of the DCoutput current of the DC-DC power converter to the smallest practicallevel by increasing the resolution of the DC output current. Thislacking resolution of the DC output current at low levels is likewise adisadvantage in numerous other applications of the DC-DC powerconverter.

The present invention provides improved resolution of the load currentby the inclusion of at least one controllable resistive path (101A,101B, 101C, 101D), or the inclusion of a least onecontrollable/programmable current source (464 on FIG. 4A), connectedbetween at least one pair of terminals of the DC-DC power converterwhere the pair of terminals is selected from the group of {the positiveoutput terminal (112), the negative output terminal (114), the positiveinput terminal (102), the negative input terminal (104). The at leastone controllable resistive path or controllable current source isconfigured to add (source) a secondary DC output current (Icon) to theprimary DC output current (Io) or subtract (sink) the secondary DCoutput current (Icon) from the primary DC output current (Io) in bothinstances in accordance with a secondary, and separate, control signal(not shown). The secondary control signal may be digital, comprising apredetermined number of bits, or analog. In one exemplary embodiment,the secondary DC output current (Icon) is suppled through thecontrollable resistive path 101D and added to the primary DC outputcurrent (Io) at the positive output terminal or node 112 such that theload current is the sum of Io and Icon. Hence, the DC input voltagesource supplies the secondary DC output current (Icon).

Certain embodiments of the invention may include an additionalcontrollable resistive path (not shown) connected in parallel withanyone of the controllable resistive paths 101A, 101B, 101C, 101D. Thecomponents and topology of the additional controllable resistive pathmay be identical to those of the at least one controllable resistivepath 101A, 101B, 101C, 101D. A resistance of the additional controllableresistive path may be adjusted by a separate control signal to provideeven higher resolution of the load current. For an example utilizing an8 bit PWM signal as the separate control signal of the additionalcontrollable resistive path will provide up to 256 steps of resolutionof the load current. If the each of the primary control signal and thesecondary control signal comprises a similar 8 bit PWM signal forcontrol purposes, the additional controllable resistive path will enablean effective resolution of the load current of 24 bit equalling 16777216steps.

The least one controllable resistive path (101A, 101B, 101C, 101D) maycomprise a resistor with adjustable resistance controlled by thesecondary control signal. The resistor may comprise a semiconductordevice such as one or more transistors, e.g. MOSFET(s), GaN, IGBT, BJT,etc., operating in linear region or triode-mode. A control terminal(s)of the one or more transistors are connected to the secondary controlsignal. The secondary control signal may comprise a DC control voltagewhich adjusts the resistance of the one or more transistors. In analternative embodiment, the secondary control signal comprises amodulated control voltage such as a PWM modulated voltage, PDM modulatedvoltage, duty-cycle/burst-mode modulated voltage (on/off control) thatswitches the semiconductor device between on-state and off-state inaccordance with a switching frequency of the modulated control voltage.Using this control mechanism, the apparent resistance of the least onecontrollable resistive path corresponds to the average on-time andon-resistance of the semiconductor device. In some embodiments, a fixedresistance, e.g. passive resistor, may be coupled in series with thesemiconductor device. The passive resistor may be dimensioned to set amaximum current through the least one controllable resistive path if theresistance of the passive resistor is significantly larger than theon-resistance of the semiconductor device, e.g. more than 10 timeslarger. The semiconductor switch still controls the level of thesecondary DC current through the secondary control signal, e.g. byadjusting its duty cycle.

The least one controllable resistive path may in some embodiments beactive simultaneously with the switched converter core 105 to provide afiner or improved resolution of the load current as graphicallyillustrated by graph 510 of FIG. 5. This effect may be achieved bydesigning the least one controllable resistive path such that themaximum secondary output current (Icon) substantially corresponds to theminimum step of the primary DC output current (Io). Depending on theresolution of the secondary DC output current (Icon), the load currentmay be incremented or decremented in small steps 511, 512, 513 etc.,hence very accurately, relatively to the previously discussed minimumvalue of 0×01, e.g. 3.9 mA, or relatively to any other value of theprimary DC output current (Io). The skilled person will understand thatthe resolution of the secondary DC output current (Icon) may be set bymultibit secondary control signal which comprises a predetermined numberof discrete steps such as between 4 steps (2 bits) and 16777216 steps(24 bits). E.g. between 256 steps (8 bits) and 65536 steps (16 bits)depending on characterises of the controllable resistive path and thesecondary control signal.

The least one controllable resistive path, or the at least onecontrollable current source, may in alternative embodiments be activewhile the switched converter core 105 is interrupted or powered-downsuch that the primary DC output current (Io) is zero. In the latterembodiment, the operation of the least one controllable resistive path,or the operation of the at least one controllable current source,extends the minimum load current (Iload) below the minimum DC outputcurrent (Io) of the switched converter core. This feature providesimproved resolution of the load current at small levels as graphicallyillustrated by graph 520 of FIG. 5. Hence, the DC-DC power converter 100is capable of providing a smooth transition in the supply of loadcurrent from an off-state to the on-state or vice versa. The powerconversion efficiency of the DC-DC power converter 100 may decrease whenthe least one controllable resistive path, or the at least onecontrollable current source, is active because a portion of some of theoutput current is dissipated in the resistance of the resistive path orin the current source. However, at very small DC load current levels thepower conversion efficiency is of lesser importance because the DC-DCpower converter 100 will rarely operate for prolonged time periods inthat state and the absolute power levels are very low.

FIG. 2 is a block diagram of a DC-DC power converter 200 in accordancewith a first embodiment of the invention. The switched converter core205 of the DC-DC power converter 200 comprises a galvanic isolationbarrier T1, e.g. a transformer or a capacitive barrier, coupling theprimary side circuit to secondary side circuit. An electrical connectionor wire 207 runs between the positive input (+) of the core 205 and thenegative output terminal 214 of the converter core to arrange the inputand output of the switched converter core in series across the DC inputvoltage Vin. The implementation and advantages of this input-outputcoupling arrangement is described in detail in PCT publication WO2015/110427. The DC-DC power converter 200 additionally comprises acontrollable resistive path 201B connected between the negative outputterminal 214 and the negative input terminal 204. The controllableresistive path 201B add a secondary DC output current (Icon) to theprimary DC output current (Io) and thereby increase the load current(iload). The secondary DC output current (Icon) is supplied by the DCinput voltage source connected between the positive and negative inputterminals 202, 204.

The switched converter core 205 may comprise a resonant high frequencyClass-DE converter operating at a switching frequency above 1 MHz, orabove 5 or above 10 MHz or even at or above 20 MHz for example in theVHF range. The switched converter core 205 may be operated in burstmode, with a PWM switch control signal that gives a proportional DCoutput current to the modulation of the PWM switch control signal. Thecontrollable resistive path 201B comprises a NMOS transistor Q100coupled in series with a resistor R100. The resistor R100 is dimensionedto limit the secondary DC output current (Icon) to at least the minimumDC output current (Io) of the switched converter core 205. In thisconfiguration Q100 can be controlled to increases it's resistance,either linearly by the magnitude/level of the secondary control signalor by a modulation of a modulated secondary control signal such that anaverage load current (Iload), i.e. the current through the LED (LOAD)will be controlled accordingly, providing the improved resolution of theload current as well as the ability to lower the minimum load current asdiscussed above in detail.

The skilled person will appreciate that the DC-DC power converter 200 incertain embodiments by include an additional, or second, controllableresistive path (not shown) connected between the negative outputterminal 214 and the negative input terminal 204. The components andtopology of the second, controllable resistive path may be identical tothe controllable resistive path 201B. A resistance of the second,controllable resistive path may be adjusted by another or third separatecontrol signal to provide even higher resolution of the load current.For an example utilizing an 8 bit PWM signal as the third separatecontrol signal will provide 256 steps of resolution of the DC currentsupplied by the second, controllable resistive path. If this resolutionimprovement is added to the corresponding resolutions of the primarycontrol signal and secondary control signal this feature will enable aneffective resolution of the load current up to 24 bits equalling16777216 discrete steps.

FIG. 3 is a block diagram of a DC-DC power converter 300 in accordancewith a second embodiment of the invention. The switched converter core305 of the DC-DC power converter 300 may comprise a high frequencyClass-E converter, but could alternatively comprise any kind of currentsourcing/outputting converter topology. The DC-DC power converter 300additionally comprises a controllable resistive path 301C connectedbetween the positive output terminal 312 and the negative outputterminal 314. The controllable resistive path 301C is thus coupled inparallel with the converter load, LOAD e.g. one or more LEDs. Thecontrollable resistive path 301C is configured to subtract a secondaryDC output current (Icon) from the primary DC output current (Io)supplied by the output of the switched converter core 305 and therebydecrease the load current (iload) in a well-controlled manner. Theadjustable resistance of the controllable resistive path 301C comprisesa series coupled NMOSFET (Q200) and resistor (R200) where the secondarycontrol signal is applied to the gate of Q200. When the switchedconverter core 305 delivers its minimum DC output current, as set by theprimary control signal, the controllable resistive path 301C can beactivated using for example a PWM signal as the secondary controlsignal. The adjustable resistance of the controllable resistive path301C will sink, or subtract, a secondary DC output current (Icon) fromthe minimum DC output current. As the minimum DC output current is fixedfor example by the time resolution of a modulated type of primary switchcontrol signal as discussed above, the secondary DC output current(Icon) is removed from the load current (Iload) to provide thepreviously discussed increased load current resolution. The skilledperson will appreciate that the DC-DC power converter 300 must be activeto enable the functionality of the controllable resistive path 301C.

FIG. 4 is a block diagram of a DC-DC power converter 400 in accordancewith a third embodiment of the invention. The switched converter core405 of the DC-DC power converter 400 may comprise a resonant convertersuch as one of a {class E, class F, class DE, class EF, LLC, LCC,SEPIC}. The DC-DC power converter 400 additionally comprises acontrollable resistive path 401D connected between a positive outputterminal 412 and a positive input terminal 402 of the DC power converter400, where the DC voltage of the positive input terminal 402 is higherthan the DC voltage of the positive output terminal 412. Thecontrollable resistive path 401D comprises a series coupled PMOSFET(Q300) and resistor (R300) to provide the adjustable resistance of theresistive path 401D. The secondary control signal comprises a modulatedcontrol signal such as the previously discussed secondary PWM controlsignal that is applied to a gate of PMOSFET (Q300) to switch Q300between on-states and off-states and control the resistance of the path.Q300 may be controlled with a small NMOS (Q301) and two resistors, R302,R301, jointly dimensioned to keep a gate voltage of PMOS Q300 within itsdesign limits.

The DC-DC power converter 400 is preferably configured as a buck orstep-down converter where the DC input voltage Vin at the positive andnegative input terminals 402, 404 is converted into a lower DC outputvoltage across the positive and negative output terminals 412, 414. Thesecondary control signal can for example be generated by a suitableprocessor such as a microprocessor connected directly to NMOS Q301 as itis ground referenced. Hence, the control network comprising the smallNMOS (Q301) and the resistors R302, R301 provides a simple interfacebetween the processor and the PMOS Q300 despite the latter is floatingrelative to circuit ground. The secondary control signal will thereforeturn-on and turn-off Q300 to add an adjustable secondary DC outputcurrent (Icon) to the DC output current (Io) of the switched core 405 toadjust the DC current to the load, LOAD. The secondary DC output current(Icon) is supplied by the DC input voltage source connected between thepositive and negative input terminals 402, 404 due to the higher DCinput voltage than DC output voltage. The skilled person will appreciatethat the functionality of the controllable resistive path 401 D isavailable independent of the operational state of the DC-DC powerconverter 400, i.e. the latter can be active or inactive e.g. powereddown or interrupted.

FIG. 4A is a block diagram of a DC-DC power converter 450 in accordancewith a fourth embodiment of the invention based on one or severalcontrollable current source(s) instead of the controllable resistivepath(s) as discussed above. The switched converter core 105 of the DC-DCpower converter 450 may comprise a galvanic isolation barrier, e.g. atransformer or a capacitive barrier, coupling the primary side circuitto secondary side circuit. The switched converter core 105 of the DC-DCpower converter 450 may comprise a high frequency Class-E or DEconverter which is switched accordance with a primary control signal(not shown) to supply a primary DC output current (Io) of the converter105. A DC input voltage Vin is supplied at the positive and negativeinput terminals 452, 454 and converted into a lower DC output voltage ora higher DC output voltage across the positive and negative outputterminals 462, 474.

The DC-DC power converter 450 additionally comprises a digitallycontrollable or programmable current source 464 in which the magnitudeand polarity of the supplied secondary DC output current Icon iscontrolled by a digital control signal 466. The digitally controllablecurrent source 464 preferably directly sets the level of the secondaryDC output current Icon. The digitally controllable current source 464may comprise a multibit current DAC or a current controlled buck. Theresolution, or minimum current step, may be determined by one LSB of thedigital control signal 466. The digital control signal may comprisebetween 2 and 16 bits and thus include between 4 and 65536 discretesteps which leads to a corresponding number of discrete steps of thesecondary DC output current Icon. The digitally controllable currentsource is connected between the positive output terminal 162 and thenegative output terminal 464 and therefore connected in parallel withthe converter load, LOAD which may comprise one or more LEDs. Thedigitally controllable current source 464 is configured to subtract thesecondary DC output current (Icon) from the primary DC output current(Io) supplied by the output of the switched converter core 105 andthereby decrease the load current (Iload) in well-controlled steps. Whenthe switched converter core 105 delivers its minimum DC output current,as set by the minimum resolution of the primary control signal, thedigitally controllable current source 464 can be activated via thedigital control signal 466 operating as a secondary control signal ofthe converter 450. The secondary DC output current (Icon) is sunk orsubtracted from the minimum DC output current and therefore increasesthe resolution of the latter by the step size of the secondary DC outputcurrent Icon.

FIG. 6 shows a transistor level diagram of an exemplary galvanicallyisolated switched converter core 605 based on a class E converter. Theswitched converter core 605 receives a DC-input voltage Vin on a primaryside or input circuit, arranged to the left of isolating transformer T1.The switched converter core 605 generates a DC output voltage and a DCoutput current Io—for example to a load via the secondary side circuit.The primary side circuit comprises a semiconductor switch arrangementQ₁, such as a MOSFET, with a control terminal that may be controlled byor driven by the previously discussed primary control signal. Theswitched converter core 605 comprises a resonant tank or network formedby capacitance C2 and the secondary side circuit comprises arectification circuit for example a class-E rectifier, here representedschematically by diode D1, capacitance C3, and inductance L3. Theprimary side and secondary side circuits are coupled by an isolatingtransformer T1. The isolation transformer T1 may comprise a PCB embeddedsolenoid transformer 500 with a primary winding 501 and a secondarywinding 502 inductively coupled to the primary winding 501, wherein thecoupling designated by the double vertical line may be a corelesscoupling.

1. A DC-DC power converter comprising: a primary side circuit comprisinga positive input terminal and a negative input terminal for receipt of aDC input voltage, a secondary side circuit comprising a positive outputterminal and a negative output terminal for supply of a load current toa load, a switched converter core operated in accordance with a primarycontrol signal to supply a primary DC output current (Io) of theconverter, said primary control signal exhibiting a minimum resolutionleading to a corresponding minimum current step of the primary DC outputcurrent, and a controllable resistive path or a controllable currentsource, wherein the controllable resistive path or the controllablecurrent source is connected between a pair of terminals selected fromthe group of: the positive output terminal, the negative outputterminal, the positive input terminal, and the negative input terminal,and wherein the controllable resistive path or the controllable currentsource is configured to add or subtract a secondary DC output current(Icon) to the primary DC output current (Io) in accordance with asecondary control signal to adjust the load current (Iload). 2-13.(canceled)
 14. The DC-DC power converter according to claim 1, whereinthe secondary control signal is configured to adjust at least one of: aresistance of the controllable resistive path to control the secondaryDC output current, and a current level or magnitude of the controllablecurrent source to directly adjust the secondary DC output current. 15.The DC-DC power converter according to claim 14, wherein the powerconverter comprises the controllable resistive path, and wherein thesecondary DC output current is adjustable between a minimum value and amaximum value by adjusting the resistance of the controllable resistivepath.
 16. The DC-DC power converter according to claim 15, wherein theminimum step of the primary DC output current is substantially equal tothe maximum value of the secondary DC output current.
 17. The DC-DCpower converter according to claim 1, wherein the power convertercomprises the controllable resistive path, wherein the controllableresistive path comprises a transistor, and wherein a control terminal ofsaid transistor is connected to the secondary control signal.
 18. TheDC-DC power converter according to claim 17, wherein the secondarycontrol signal comprises: a DC voltage, or a modulated control voltage.19. The DC-DC power converter according to claim 18, wherein themodulated voltage comprises a PWM modulated voltage, a PDM modulatedvoltage, or a duty-cycle/burst-mode modulated voltage.
 20. The DC-DCpower converter according to claim 19, wherein the modulated controlvoltage is derived from a multibit control signal for controlling amodulation of the PWM modulated voltage or the PDM modulated voltage.21. The DC-DC power converter according to claim 17, wherein thetransistor comprises a MOSFET operating in its linear region oroperating in triode-mode.
 22. The DC-DC power converter according toclaim 1, wherein the primary control signal comprises a modulated switchcontrol signal.
 23. The DC-DC power converter according to claim 22,wherein the modulated switch control signal comprises a PWM modulatedcontrol voltage, a PDM modulated control voltage, a PAM modulatedcontrol voltage, or a duty-cycle/burst-mode modulated control voltage.24. The DC-DC power converter according to claim 1, wherein the switchedconverter core comprises a semiconductor switch arrangement having acontrol input connected to the primary control signal and an outputcoupled to an inductive network.
 25. The DC-DC power converter accordingto claim 1, wherein the power converter comprises the controllableresistive path, and wherein the controllable resistive path is connectedbetween the positive output terminal and negative output terminal tosubtract the secondary DC output current from the primary DC outputcurrent and thereby decrease the load current.
 26. The DC-DC powerconverter according to claim 1, wherein the power converter comprisesthe controllable resistive path, wherein the switched converter core isconfigured to step-down the DC input voltage, and wherein saidcontrollable resistive path is connected between the positive inputterminal and the positive output terminal to add the secondary DC outputcurrent to the primary DC output current and thereby increase the loadcurrent.
 27. The DC-DC power converter according to claim 1, wherein thepower converter comprises the controllable resistive path, wherein theswitched converter core comprises: a galvanic isolation barrier couplingthe primary side circuit to secondary side circuit, and an electricalconnection between the positive input terminal and the negative outputterminal to arrange the input and output of the switched converter corein series across the DC input voltage, and wherein said controllableresistive path is connected between the positive output terminal and thenegative input terminal to add the secondary DC output current to theprimary DC output current and thereby increase the load current.
 28. TheDC-DC power converter according to claim 1, wherein the switchedconverter core comprises a resonant class DE converter, a resonant classE converter, or a resonant SEPIC converter.
 29. The DC-DC powerconverter according to claim 1, wherein the minimum resolution comprisesa minimum time step.